This s-parameters tutorial consists of two parts: Part I discusses the fundamental background needed to understand the concept of s-parameters; Part II (to appear in the next issue of In Compliance magazine) explains the s-parameters use in EMC measurements and testing.
The background needed for the study of s-parameters consists of two fundamental topics:
- two-port networks,
- reflections on transmission lines.
Two-Port Network Theory
Two-port network theory is a circuit analysis technique that is different from the majority of other approaches. Most circuit analysis approaches (Kirchhoff’s laws, node voltage/mesh current methods, superposition, and others) provide a way of calculating voltages and currents anywhere in the circuit. Thevenin or Norton theorems allow us to obtain an equivalent circuit model with respect to the specified pair of terminals (usually the output terminals, or the output port) of the network.
Another way of describing the circuit with respect to the two terminals is by treating the network as a two-port circuit. In many electrical circuits obtaining voltages and currents at the input and output ports, instead of any point in the circuit, is more convenient and practical. Thus, the fundamental principle underlying the two-port circuit analysis is that only the terminal variables (input voltage/current and output voltage/current) are of interest. We are not interested in calculating voltages and current inside the circuit.
In EMC the two-port network analysis is usually carried in a sinusoidal steady-state where the voltages and currents are sinusoids and as such, at each frequency, are described by their amplitudes and phases. It turns out that such an analysis can be easily performed using complex numbers, called phasors, (instead of real time functions) which represent these amplitudes and phases. To differentiate a complex variable from a real variable let’s place a “hat” above it. Thus, V and I denote real variables, while and correspond to the complex ones. Figure 1 shows the basic building block of a two-port network.
Figure 1: Two-port network
Of the four terminal variables only two are independent. Thus, for any two-port network, once we specify two of the four variables, the other two can be obtained. It follows that the description of a two-port network requires only two simultaneous equations.
There are six different ways to write the two equation involving the four variables; this is shown in Eq. (1).
(1)
The coefficients in each set of equations in Eq. (1) are called the parameters of the two-port network. We refer to them as the z parameters, y parameters, a parameters, b parameters, h parameters, or the g parameters of the network. All parameter sets contain the same information about a network, and it is always possible to calculate any set in terms of any other set.
The question is: How do we obtain a particular set of parameters? Let’s begin with the z parameters used in Eq. (1). These parameters can be obtained from Eq. (2a) as
(2a)
Thus, the z parameters can be obtained from the voltage and current measurements when each port, one at a time, is open-circuited.
The y parameters are obtained from Eq. (2b) as
(2b)
Thus, the y parameters can be obtained from the voltage and current measurements when each port, one at a time, is short-circuited. The remaining port parameters are obtained in a similar manner.
The a parameters are obtained from Eq. (2c) as
(2c)
Thus, to obtain the a parameters, both the open-circuit and short-circuit measurements at port 2 are needed.
The b parameters are obtained from Eq. (2d) as
(2d)
Thus, to obtain the b parameters, both the open-circuit and short-circuit measurements at port 1 are needed.
The h parameters are obtained from Eq. (2e) as
(2e)
Thus, to obtain the h parameters, we need the open-circuit measurements at port 1 and short-circuit measurements at port 2.
Finally, the g parameters are obtained from Eq. (2f) as
(2f)
Thus, to obtain the g parameters, we need the short-circuit measurements at port 1 and open-circuit measurements at port 2. Table 1 summarizes the results for each parameter set.
Parameter Set: | |||||||||||
z | y | a | b | h | g | ||||||
Port 1 | Port 2 | Port 1 | Port 2 | Port 1 | Port 2 | Port 1 | Port 2 | Port 1 | Port 2 | Port 1 | Port 2 |
open | open | short | short |
Not used |
Open short |
Open short |
Not used |
open | short | short | open |
Table 1: Parameter set measurements
In summary, to obtain any set of parameters we need two measurements. These measurements are either at the same port, or two different ports, when the port is either short- or open-circuited.
Each parameter set contains the same information and all sets are related to each other. This means that we can always obtain one set from another through algebraic transformations.
When the required measurement for a specific set of parameters cannot be made, we can always substitute any other measurement from Table 1, and determine the missing parameters through algebraic transformations.
In the typical application of a two-port network, the circuit is driven at port 1 and terminated by a load at port 2, as shown in Figure 2.
Figure 2: Typical two-port circuit
In this case, we are usually interested in determining the port 2 voltage and current _{2}, _{2} in terms of the two-port parameters and _{S}, _{S} and _{L}. These terminal currents and voltages give rise to several characteristics describing this two-port network:
- Input impedance _{in} = _{1}/_{1}
- Output impedance _{out} = _{2}/_{2}, (_{G} = 0)
- Current gain _{2}/_{1}
- Voltage gain _{2}/_{1}
Any set of parameters can be used to derive the above characteristics. The expressions for the above characteristics, using the z-parameter set, are shown in Eq. (3), [1].
(3)
Thus, in the two-port circuit analysis we can determine the required characteristics of the network from the short and/or open circuit voltage and current measurements at the port(s).
Reflections on Transmission Lines
To facilitate the discussion of s-parameters in the next section we need to be familiar with the transmission line phenomena of reflections. We begin by reviewing the reflections at the load and at the source, and then proceed to the reflections at a discontinuity along the transmission line.
Consider the transmission line circuit shown in Figure 3. A sinusoidal voltage source, _{S}, with internal impedance _{S}, drives a transmission line with characteristic impedance _{C} and length L, terminated with a load _{L}. When the switch closes a forward voltage, ^{+} and current wave, ^{+}, originate at z = 0 and travel towards the load, [2].
Note: (z) and (z) denote the total complex voltage and current, respectively, at any location z along the line.
Figure 3: Transmission line circuit and a forward wave
Upon arrival at the load a reflected wave is generated, as shown in Figure 4.
Figure 4: Reflection at the load
The voltage of the reflected wave is related to the voltage of the incident wave by
(4)
where, _{L} is the voltage reflection coefficient at the load, given by
(5)
The total voltage at the load is the sum of the incident voltage and the reflected voltage. When the load is matched to the transmission line (_{L} = _{C}) the reflection coefficient is zero, and therefore there is no reflected voltage.
When the line is not matched at the load, a reflected wave, ^{–}, is created and travels back to the source. Upon the arrival at the source this wave gets reflected again, creating a forward voltage wave ^{-+}; this is shown in Figure 5.
Figure 5: Reflection at the source
The voltage of the reflected wave,^{-+} is related to the voltage of the incident wave,^{–} by
(6)
where, _{S} is the voltage reflection coefficient at the source, given by
(7)
When the source is matched to the transmission line (_{S} = _{C}) the reflection coefficient is zero, and therefore there is no reflected voltage at the source.
Next, let’s discuss the reflections along a transmission line discontinuity. Discontinuity along a transmission line can be caused by many different factors. The easiest case to consider is when the characteristic impedance of the transmission line changes (from _{C1} to _{C2}), as shown in Figure 6.
Figure 6: Reflections at a discontinuity
When the incident wave traveling on transmission line 1 arrives at the junction it creates a reflected wave and a transmitted wave. The voltage of the reflected wave is related to the voltage of the incident wave by
(8)
where, _{12} is the voltage reflection coefficient, given by
(9)
The voltage of the transmitted wave is related to the voltage of the incident wave by
(10)
where, _{12} is the voltage transmission coefficient given by
(11)
S-Parameters
To introduce s-parameters (also known as scattering parameters) we will combine the two-port networks approach and the transmission line reflections. Recall: using two-port network approach we can obtain the relevant information about the network by taking either short or open circuit measurements at its ports. This approach works well for the low frequency signals. When high frequencies are present creating a true short or true open at a port presents a formidable task because of the parasitic inductance and capacitance.
To characterize high-frequency circuits we use s parameters which relate traveling voltage waves that are incident, reflected and transmitted when a two-port network is inserted into a transmission line. This is depicted in Figure 7.
Figure 7: Traveling waves impinging on: a) port 1, b) port 2
The incident waves (which give rise to the reflected and transmitted waves) can be impinging on either port 1 or port 2. Let’s denote the wave incident on port 1 and port 2 by _{1} and _{2}, respectively. These waves give rise to the reflected waves, _{1} and _{2}, as shown in Figure 8.
Figure 8: Incident and reflected waves at port 1 and port 2
The incident and reflected waves are used to define s parameters for a two port network. The linear equations describing this two-port network in terms of the s parameters are
(12)
That is, s parameters define the reflected wave at a particular port in terms as of the incident wave at each port.
(Note: s parameters are complex numbers and as such, technically, we should denote them with a hat, i.e., as . In vast majority of the EMC literature the s parameters are denoted without a hat, with the implied understanding that they are complex numbers. We will follow this convention).
The incident and reflected waves are related to the voltage and current waves at each port as [2], [3]
(13a)
(13b)
where _{C} is the characteristic impedance of the transmission line connected to the two-port network.
The s-parameters in Eq. (12), which related to the voltages and currents at each port by Eqs. (13), are referred to as simply the s parameters (as opposed to the generalized s parameters defined next).
In many applications (especially in EMC) it is convenient to use normalized waves defined by
(14a)
(14b)
Such waves are called the power waves, and the s parameters, when related to the voltages and currents at each port by Eqs. (14), are called the generalized s parameters.
We obtain the s parameters from Eq. (12) in a manner similar to that used for the two-port parameter sets discussed in Part I. That is,
(15)
When evaluating the two-port network parameter sets in part I, we selectively measured a voltage or current at a given port, when one or both ports where either open- or short-circuited (see Table 1). When evaluating the s parameters we cannot use open- or short-circuited measurements as they are not reliable at high frequencies. So how do we translate Eq. (15) into a practical application?
Let’s explain the meaning of Eq. (15) by looking at the typical application of a two-port network, shown in Figure 9.
Figure 9: Typical two-port circuit application: a) circuit driven at port 1 and terminated by a load at port 2, b) circuit driven at port 2 and terminated by a load at port 1
In Figure 9a, the incident wave, _{1}, arrives at port 1 where it creates a reflected wave, _{1}, and a transmitted wave _{2}. The reflected wave travels back to the source. If the source is matched to the transmission line (_{S} = _{C}), there is no reflection at the source and thus no other wave will travel to port 1.
The transmitted wave, _{2} travels to the load connected to port 2 with a transmission line. If the load is not matched to the transmission line (_{S} ≠ _{C}), a reflection will take place and a reflected wave, _{2}, will travel towards port 2. On the other hand, if the load is matched to the transmission line, there is no reflection at the load and therefore no wave will be incident on port 2. The circuit in Figure 9b can be described in a similar manner.
Now, we are ready to investigate each individual s parameter. The parameter s_{11} is obtained from
(16a)
Thus, s_{11} is the port 1 reflection coefficient, when the incident wave on port 2 is zero, which means that port 2 should be terminated in matched load (_{L} = _{C}) to avoid reflections. This is shown in Figure 10.
Figure 10: a) Circuit for determining s_{11} or s_{21} b) alternative circuit for determining s_{11}
Note that the parameter s_{11} can be determined from two different circuit configurations: a) with the load connected at the end of a matched transmission line, and b) with the matching load connected directly to port 2.
The parameter s_{21} is obtained from
(16b)
Thus, s_{21} is the transmission coefficient from port 1 to port 2, with port 2 terminated in matched load, as shown in Fig. 10a.
To obtain the parameters s_{22} and s_{12} we use the circuits shown in Figure 11.
Figure 11: a) Circuit for determining s_{22} or s_{12} b) alternative circuit for determining s_{22}
Since,
(16c)
It follows that s_{22} is the port 2 reflection coefficient, when the incident wave on port 1 is zero, as shown in Figure 11.
Finally,
(16d)
Thus, s_{12} is the transmission coefficient from port 2 to port 1, with port 1 terminated in matched load, as shown in Fig. 11.
When generalized s parameters are used, we can also describe a two-port network in terms of the incident, reflected and transmitted powers. When we normalize the waves (power waves) we obtain the so-called generalized s-parameters and we can relate these s parameters to the incident and reflected powers. These powers are related to the incident, and transmitted waves at each port as follows:
_{} = |_{1}|^{2} is the power incident on port 1,
_{} = |_{1}|^{2} is power reflected from port 1,
_{} = |_{2}|^{2} is the power incident on port 2,
_{} = |_{2}|^{2} is power reflected from port 2.
Thus, we can relate the generalized s parameters to the powers as follows.
(17a)
(17b)
(17c)
(17d)
We can express several gains and losses (in dB) in terms of s parameters. The most common gains (losses) in EMC are:
Return Loss:
(18)
Insertion loss (or gain):
(19)
Part II of the s-parameters tutorial will describe the application of s parameters in the EMC measurements and testing.
References
- Nilsson, J. W. and Riedel, S. A., Electric Circuits, 10^{th} ed., Pearson, Upper Saddle River, NJ, 2015.
- Bogdan Adamczyk, Foundations of Electromagnetic Compatibility with Practical Applications, Wiley, 2017.
- Ludwig, R. and Bogdanov, G., RF Circuit Design, 2^{nd} ed., Pearson, Upper Saddle River, NJ, 2009.
Dr. Bogdan Adamczyk is a professor and the director of the EMC Center at Grand Valley State University (http://www.gvsu.edu/emccenter) where he performs EMC precompliance testing for industry and develops EMC educational material. He is an iNARTE certified EMC Master Design Engineer, a founding member and the chair of the IEEE EMC West Michigan Chapter. Prof. Adamczyk is the author of the textbook “Foundations of Electromagnetic Compatibility with Practical Applications” (Wiley, 2017). He can be reached at adamczyb@gvsu.edu.
Part I next part next month