Foundations
When two circuits are in the vicinity of one another, a signal propagating in one circuit can induce a signal in another circuit, due to capacitive (electric field) and/or inductive (magnetic field) coupling between the circuits. This phenomenon is referred to as crosstalk. An example of such an arrangement is shown in Figure 1.
Two PCB traces in a microstrip configuration are separated from each other by distance s, and from the ground plane (which is return conductor for both) by a distance d. The first trace (generator conductor) is driven by a time-varying voltage source, V_{S} with the impedance R_{S}, and terminated by a load resistor, R_{L}. The second trace (receptor) is terminated by the load resistors, R_{NE} and R_{FE}, on the near end and the far end, respectively. This arrangement can be modeled by the circuit shown in Figure 2.
The time-varying current on the generator line, I_{G}, creates a magnetic field that gives rise to the magnetic flux that penetrates the loop between the two receptor conductors inducing a voltage in the receptor circuit. We model this by the mutual inductance L_{GR} as shown in Figure 3. (Note: this model is valid for electrically short lines, as we represent the induced voltage as a lumped source).
Similarly, the time-varying voltage between the two conductors of the generator circuit, V_{G}, gives rise to the electric field lines, some of which terminate on the conductors of the receptor circuit inducing a current in the receptor circuit. We model this by the mutual capacitance C_{GR} as shown in Figure 4.
Superposition of the two coupling mechanisms results in the circuit shown in Figure 5.
By superposition, the near- and far-end voltages are given by
1a
1b
Under the assumption of the line being electrically short at the highest significant frequency component of V_{S}(t) the generator line voltage and current are essentially constant along the line. Thus,
2a
2b
and, therefore,
3a
3b
Thus, to minimize crosstalk we can reduce: 1) the variation of the source signal, 2) the inductive coupling, L_{GR}, or, 3) the capacitive coupling, C_{GR}.
Verification
The experimental setup for crosstalk measurements is shown in Figure 6.
PCB with different circuit topologies is shown in Figure 7.
Three different circuit topologies were investigated, and are described in Table 1.
Case |
Line separation s [mils] |
Distance to |
1 |
25 |
54.8 |
2 |
25 |
12 |
3 |
75 |
12 |
Table 1: Circuit topologies
Figures 8 through 10 show the generator (aggressor) signal as well as the resulting near- and far-end voltages induced on the receptor (victim) line.
The source has an open-circuit voltage that is a 1-V_{pp}, 1-MHz trapezoidal pulse train having 100-ns rise time, 200-ns fall time, and a 50% duty cycle. We make the following observation in Case 1, presented Figure 8.
Voltage induced on the near end during the rise time is while the voltage induced during the fall time . Since the value of the rise time is twice that of the fall time, according to Equation 3a, the induced voltages should differ in magnitude by a factor of two, which indeed is the case. We also note that the polarities of the two voltages are opposite, which is to be expected from Equation 3a. Similar observations can be made for the voltages induced on the far end. Furthermore, since the coefficients of coupling for the near-end voltage (Equation 3a) are positive, the induced-voltage during the rise is also positive. The far-end voltage is negative during the rise time, indicating that the inductive coupling dominates the capacitive one (see Equation 3b).
Bringing the ground plane closer to the lines, while keeping the distance between the lines unchanged (Case 2), predominantly reduces inductive coupling and results in a reduction of the induced voltage magnitudes, as shown in Figure 9.
Case 3 depicts the scenario where the distance to the ground plane is unchanged from Case 2, but the separation between the lines is increased. This predominantly reduces capacitive coupling and results in further reduction of the induced voltages, as shown in Figure 10.
References
[1] Clayton R. Paul, Introduction to Electromagnetic Compatibility, Wiley, 2006. [2] Henry W. Ott, Electromagnetic Compatibility Engineering, Wiley, 2009. [3] Bogdan Adamczyk, Foundations of Electromagnetic Compatibility with Practical Applications, Wiley, 2017. [4] Bill Spence and Pete Vander Wel, Designers of the PCB used for Crosstalk Measurements, Gentex Corp, 2008
Dr. Bogdan Adamczyk is a professor and the director of the EMC Center at Grand Valley State University (GVSU). He is also the founder and principal educator of EMC Educational Services LLC (www.emcspectrum.com) which specializes in EMC courses for the industry. Prof. Adamczyk is the author of the upcoming book “Foundations of Electromagnetic Compatibility with Practical Applications” (Wiley, 2017). He can be reached at profbogdan@emcspectrum.com.
Jim Teune is a founding partner of E3 Compliance LLC which specializes in product development and EMC precompliance testing. He is an iNARTE certified EMC Engineer and Master EMC Design Engineer. Jim is an industrial partner of the EMC Center at GVSU.
He can be reached at jim@e3compliance.com.
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